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TS1001 page 1 ? 2011 touchstone semiconductor, inc. all rights reserved. features single 0.65v to 2.5v operation supply current: 0.6 a (typ) offset voltage: 0.5mv (typ) low tcv os : 20v/c (max) a vol driving 100k ? load: 90db (min) unity gain stable rail-to-rail input and output no output phase reversal 5-pin sc70 package applications battery/solar-powered instrumentation portable gas monitors low-voltage signal processing nanopower active filters wireless remote sensors battery-powered industrial sensors active rfid readers powerline or battery current sensing handheld/portable pos terminals description the TS1001 is the industry?s first sub-1a supply current, precision cmos operational amplifier rated to operate at a nominal supply voltage of 0.8v. optimized for ultra-long-life battery-powered applications, the TS1001 is touchstone?s first operational amplifier in the ?nanowatt analog?? high-performance analog integrated circuits portfolio. the TS1001 exhibits a typical input offset voltage of 0.5mv, a typical input bias current of 25pa, and rail- to-rail input and output stages. the TS1001 can operate from single-supply voltages from 0.65v to 2.5v. the TS1001?s combined features make it an excellent choice in applications where very low supply current and low operating supply voltage translate into very long equipment operating time. applications include: nanopower active filters, wi reless remote sensors, battery and powerline current sensors, portable gas monitors, and handheld/portable pos terminals. the TS1001 is fully specified at v dd = 0.8v and over the industrial temperature range ( ? 40c to +85c) and is available in a pcb-space saving 5-lead sc70 surface-mount package. 0.53 0.58 0.63 0.68 0.73 percent of units - % 30% 25% 20% 15% 10% 5% 0% supply current distribution supply current - a the only 0.8v/0.6a rail-to-rail op amp typical application circuit a nanowatt 2-pole sallen ke y low pass filter patent(s) pending nanowatt analog and the touchstone semiconductor logo are registered trademarks of touchstone semiconductor, incorporated. v dd = 0.8v
TS1001 page 2 TS1001ds r1p0 rtfds absolute maximum ratings total supply voltage (v dd to v ss ) ........................... +2.75 v voltage inputs (in+, in-) ........... (v ss - 0.3v) to (v dd + 0.3v) differential input voltage .......................................... 2.75 v input current (in+ , in-) .............................................. 20 ma output short-circuit dura tion to gnd .................... indefinite continuous power dissipation (t a = +70c) 5-pin sc70 (derate 3.87mw/c above +70c) .. 310 mw operating temper ature range .................... - 40c to +85c junction temper ature .............................................. +150c storage temperature rang e ..................... -65c to +150c lead temperature (sol dering, 10s ) ............................. +300 electrical and thermal stresses beyond those listed under ?absolute maximum ratings? ma y cause permanent damage to the device. these are stress ratings only and functional operation of the device at these or any other condition beyond those indicated in the op erational sections of the specifications is not implied. ex posure to any absolute maximum rating conditions for extended periods may affect device reliability and lifetime. package/ordering information tape & reel order number part marking package quantity TS1001ij5t tae 3000 lead-free program: touchstone semiconductor supp lies only lead-free packaging. consult touchstone semiconductor for products s pecified with wider operating temperature ranges.
TS1001 TS1001ds r1p0 page 3 rtfds electrical characteristics v dd = +0.8v, v ss = 0v, v incm = v ss ; r l = 100k ? to (v dd -v ss )/2; t a = -40c to +85c, unless otherwise noted. typical values are at t a = +25c. see note 1 parameters symbol conditions min typ max units supply voltage range v dd -v ss 0.65 0.8 2.5 v supply current i sy r l = open circuit t a = 25 c 0.6 0.8 a -40 c t a 85 c 1 input offset voltage v os v in = v ss or v dd t a = 25 c 0.5 3 mv -40 c t a 85 c 6 input offset voltage drift tcv os 20 v/c input bias current i in+ , i in- v in+ , v in- = (v dd - v ss )/2 t a = 25 c 0.025 na -40 c t a 85 c 20 input offset current i os specified as i in+ - i in- v in+ , v in- = (v dd - v ss )/2 t a = 25 c 0.01 na -40 c t a 85 c 2 input voltage range ivr guaranteed by input offset voltage test v ss v dd v common-mode rejection ratio cmrr 0v v in ( cm ) 0.4v 50 74 db power supply rejection ratio psrr 0.65v (v dd - v ss ) 2.5v 50 74 db output voltage high v oh specified as v dd - v out , r l = 100k ? to v ss t a = 25 c 1.2 2 mv -40 c t a 85 c 2.5 specified as v dd - v out , r l = 10k ? to v ss t a = 25 c 10 16 -40 c t a 85 c 20 output voltage low v ol specified as v out - v ss , r l = 100k ? to v dd t a = 25 c 0.4 0.6 mv -40 c t a 85 c 1 specified as v out - v ss , r l = 10k ? to v dd t a = 25 c 5 7 -40 c t a 85 c 10 short-circuit current i sc+ v out = v ss t a = 25 c 0.5 1.5 ma -40 c t a 85 c 0.3 i sc- v out = v dd t a = 25 c 4.5 11 -40 c t a 85 c 3 open-loop voltage gain a vol v ss +50mv v out v dd -50mv t a = 25 c 90 104 db -40 c t a 85 c 85 gain-bandwidth product gbwp r l = 100k ? to v ss , c l = 20pf 4 khz phase margin m unity-gain crossover, r l = 100k ? to v ss , c l = 20pf 70 degrees slew rate sr r l = 100k ? to v ss, a vcl = +1v/v 1.5 v/ms full-power bandwidth fpbw fpbw = sr/( ? v out,pp ); v out,pp = 0.7v pp 680 hz input voltage noise density e n f = 1khz 0.6 v/ note 1: all specifications are 100% tested at t a = +25c. specification lim its over temperature (t a = t min to t max ) are guaranteed by device characterization, not production tested.
TS1001 page 4 TS1001ds r1p0 rtfds typical performance characteristics supply current vs supply voltage supply curent - a supply voltage - volt supply current vs input common-mode voltage supply curent - a input common-mode voltage - volt supply current vs input common-mode voltage input offset voltage vs input common-mode voltage input offset voltage - mv input offset voltage - mv input common-mode voltage - volt input offset voltage vs supply voltage input common-mode voltage - volt supply curent - a supply voltage - volt v dd =0.8v t a = +25 c input offset voltage vs input common-mode voltage input offset voltage - mv input common-mode voltage - volt v dd = 2.5v t a = +25 c +25c +85c -40c 0.3 0.4 0.5 0.6 0.7 0.8 t a = +25 c 0.65 0.6 0.55 0.5 0 0.2 0.4 0.6 0.8 t a = +25 c 0.65 0.6 0.55 0.5 0 0.5 1.5 2 2.5 1 t a = +25 c 0.5 1.5 2 2.5 1 v incm = v dd 0.65 0.6 0.55 0.5 0.55 v incm = 0v 0 0.2 0.4 0.6 0.8 1 0.5 0 -1 -0.5 1 0.5 0 -1 -0.5 0 0.5 1.5 2 2.5 1 0.8 1.2 0.65 2.5
TS1001 TS1001ds r1p0 page 5 rtfds -40 typical performance characteristics input bias current (i in+ , i in- ) vs input common-mode voltage input bias current - p a input common-mode voltage - volt output voltage high (v oh ) vs temperature, r load =100k ? temperature - c output voltage low (v ol ) vs temperature, r load =100k ? temperature - c output voltage high (v oh ) vs temperature, r load =10k ? output voltage low (v ol ) vs temperature, r load =10k ? input bias current (i in+ , i in- ) vs input common-mode voltage output saturation voltage - mv input common-mode voltage - volt input bias current - p a output saturation voltage - mv v dd = 2.5v t a = +25 c v dd =0.8v t a = +25 c 0 0.2 0.4 0.6 0.8 0 0.5 1.5 2 2.5 1 100 75 25 -50 -25 0 50 250 200 100 -50 0 50 150 r l = 100k ? v dd = 0.8v v dd = 2.5v r l = 100k ? v dd = 0.8v v dd = 2.5v 4.5 4 2 0 1 3 3.5 0.5 1.5 2.5 1.8 1.6 0.8 0 0.4 1.2 1.4 0.2 0.6 1 +25 +85 -40 +25 +85 20 0 10 30 35 5 15 25 output saturation voltage - mv output saturation voltage - mv temperature - c temperature - c -40 +25 +85 -40 +25 +85 r l = 10k ? v dd = 0.8v v dd = 2.5v r l = 10k ? v dd = 0.8v v dd = 2.5v 16 0 8 4 12 20
TS1001 page 6 TS1001ds r1p0 rtfds typical performance characteristics output short circuit current, i sc+ vs temperature output short-circuit current - ma output short circuit current, i sc- vs temperature large-signal transient response v dd = 2.5v, v ss = gnd, r load = 100k ? , c load = 15pf 200 s/div output short-circuit current - ma input small-signal transient response v dd = 2.5v, v ss = gnd, r load = 100k ? , c load = 15pf 2ms/div output input output temperature - c temperature - c -40 +25 +85 -40 +25 +85 v dd = 0.8v v dd = 2.5v v dd = 0.8v v dd = 2.5v v out = 0v v out = v dd 25 15 0 5 10 20 50 30 0 10 20 40 60 70 gain and phase vs. frequency gain - db frequency - hz phase - de g rees 10 1k 10k 100 40 -20 0 20 60 50 -250 -150 -50 150 100k v dd = 0.8v t a = +25 c r l = 100k ? c l = 20pf a vcl = 1000 v/v phase gain 4khz 70
TS1001 TS1001ds r1p0 page 7 rtfds pin functions pin label function 1 out amplifier output. 2 v ss negative supply or analog gnd. if applying a negative voltage to this pin, connect a 0.1f capacitor from this pin to analog gnd. 3 +in amplifier non-inverting input. 4 -in amplifier inverting input. 5 v dd positive supply connection. connect a 0.1f bypass capacitor from this pin to analog gnd. theory of operation the TS1001 is fully functional for an input signal from the negative supply (v ss or gnd) to the positive supply (v dd ). the input stage consists of two differential amplifiers, a p-channel cmos stage and an n-channel cmos stage that are active over different ranges of the input common mode voltage. the p-channel input pair is active for input common mode voltages, v incm , between the negative supply to approximately 0.4v below the positive supply. as the common-mode input voltage moves closer towards v dd , an internal current mirror activates the n-channel input pair differential pair. the p-channel input pair becomes inactive for the balance of the input common mode voltage range up to the positive supply. because both input stages have their own offset voltage (v os ) characteristic, the offset voltage of the TS1001 is a function of the applied input common-mode voltage, v incm . the v os has a crossover point at ~0.4v from v dd (refer to the v os vs. v cm curve in the typical operating characteristics section). caution should be taken in applications where the input signal amplitude is comparable to the TS1001?s v os value and/or the design requires high accuracy. in these situations, it is necessary for the input signal to avoid the crossover point. in addition, amplifier parameters such as psrr and cmrr which involve the input offset voltage will also be affected by changes in the input common-mode voltage across the differential pair transition region. the second stage is a folded-cascode transistor arrangement that conv erts the input stage differential signals into a single-ended output. a complementary drive generator supplies current to the output transistors that swing rail to rail. the TS1001 output stages voltage swings within 1.2mv from the rails at 0.8v supply when driving an output load of 100k ? - which provides the maximum possible dynamic range at the output. this is particularly important when operating on low supply voltages. when driving a stiffer 10k ? load, the TS1001 swings within 10mv of v dd and within 5mv of v ss (or gnd). applications information portable gas detecti on sensor amplifier gas sensors are used in many different industrial and medical applications. gas sensors generate a current that is proportional to the percentage of a particular gas concentration sensed in an air sample. this output current flows through a load resistor and the resultant voltage drop is amplified. depending on the sensed gas and sensitivity of the sensor, the output current can be in the range of tens of microamperes to a few milliamperes. gas sensor datasheets often specify a recommended load resistor value or a range of load resistors from which to choose. there are two main applications for oxygen sensors ? applications which sense oxygen when it is abundantly present (that is, in air or near an oxygen tank) and those which detect traces of oxygen in parts-per-million concent ration. in medical applications, oxygen sensors are used when air quality or oxygen delivered to a patient needs to be monitored. in fresh air, the concentration of oxygen is 20.9% and air samples containing less than 18% oxygen are considered dangerous. in industrial applications, oxygen sensors are used to detect the absence of oxygen; for example, vacuum-packaging of food products is one example.
TS1001 page 8 TS1001ds r1p0 rtfds the circuit in figure 1 illustrates a typical implementation used to amplify the output of an oxygen detector. the TS1001 makes an excellent choice for this application as it only draws 0.6a of supply current and operates on supply voltages down to 0.65v. with the components shown in the figure, the circuit consumes less than 0.7 a of supply current ensuring that small form- factor single- or button-cell batteries (exhibiting low mah charge ratings) could last beyond the operating life of the oxygen sensor. the precision specifications of the TS1001, such as its low offset voltage, low tcv os , low input bias current, high cmrr, and high psrr are other factors which make the TS1001 an excellent choice for this application. since oxygen sensors typically exhibit an operating life of one to two years, an oxygen sensor amplifier built around a TS1001 can operate from a conventionally-available single 1.5-v alkaline aa battery for over 290 years! at such low power consumption from a single cell, the oxygen sensor could be replaced over 150 times before the battery requires replacing! nanowatt, buffered single-pole low-pass filters when receiving low-level signals, limiting the bandwidth of the incoming signals into the system is often required. as shown in figure 2, the simplest way to achieve this objective is to use an rc filter at the noninverting terminal of the TS1001. if additional attenuation is needed, a two-pole sallen-key filter can be used to provide the additional attenuation as shown in figure 3. for best results, the filter ?s cutoff frequency should be 8 to 10 times lower than the TS1001?s crossover frequency. additional operational amplifier phase margin shift can be avoided if the amplifier bandwidth-to-signal bandwidth ratio is greater than 8. the design equations for the 2-pole sallen-key low- pass filter are given below with component values selected to set a 400hz low-pass filter cutoff frequency: r1 = r2 = r = 1m ? c1 = c2 = c = 400pf q = filter peaking factor = 1 f?3db = 1/(2 x x rc) = 400 hz r3 = r4/(2-1/q); with q = 1, r3 = r4. a single +1.5 v supply, two op amp instrumentation amplifier the TS1001?s ultra-low supply current and ultra-low voltage operation make it ideal for battery-powered applications such as the instrumentation amplifier shown in figure 4. the circuit utilizes t he classic two op amp instrumentation amplifier t opology with four resistors figure 2: a simple, single-pole active low-pass filter. figure 3: a nanopower 2-pole sallen-key low-pass filter. figure 4: a two op amp instrumentation amplifier. figure 1 : a nanopower, precision oxygen gas sensor amplifier.
TS1001 TS1001ds r1p0 page 9 rtfds to set the gain. the equation is simply that of a noninverting amplifier as shown in the figure. the two resistors labeled r1 should be closely matched to each other as well as both resistors labeled r2 to ensure acceptable common-mode rejection performance. resistor networks ensure the closest matching as well as matched drifts for good temperature stability. capacitor c1 is included to limit the bandwidth and, therefore, the noise in sensitive applications. the value of this capacitor should be adjusted depending on the desired closed-loop bandwidth of the instrumentation amplifier. the rc combination creates a pole at a frequency equal to 1/(2 r1c1). if the ac-cmrr is critical, then a matched capacitor to c1 should be included across the second resistor labeled r1. because the TS1001 accepts rail-to-rail inputs, the input common mode range includes both ground and the positive supply of 1.5v. furthermore, the rail-to-rail output range ensures the widest signal range possible and maximizes the dynamic range of the system. also, with it s low supply current of 0.6 a, this circuit consumes a quiescent current of only ~1.3 a, yet it still exhibits a 1-khz b andwidth at a circuit gain of 2. driving capacitive loads while the TS1001?s internal gain-bandwidth product is 4khz, it is capable of driv ing capacitive loads up to 50pf in voltage follower c onfigurations without any additional components. in many applications, however, an operational amplifier is required to drive much larger capacitive loads. the amplifier?s output impedance and a large capacitive load create additional phase lag that further reduces the amplifier?s phase margin. if enough phase delay is introduced, the amplifier?s phase margin is reduced. the effect is quite evident when the transient response is observed as there will appear noticeable peaking/ringing in the output transient response. if the TS1001 is used in an application that requires driving larger capacitive loads, an isolation resistor between the output and the capacitive load should be used as illustrated in figure 5. table 1 illustrates a range of r iso values as a function of the external c load on the output of the TS1001. the power supply voltage used on the TS1001 at which these resistor values were determined empirically was 1.8v. the oscilloscope capture shown in figure 6 illustrates a typical transient response obtained with a c load = 500pf and an r iso = 50k ? . note that as c load is increased a smaller r iso is needed for optimal transient response. in the event that an external r load in parallel with c load appears in the application, the use of an r iso results in gain accuracy loss because the external series r iso forms a voltage-divider with the external load resistor r load . external capacitive load, c load external output isolation resistor, r iso 0-50pf not required 100pf 120k ? 500pf 50k ? 1nf 33k ? 5nf 18k ? 10nf 13k ? figure 5: using an external resistor to isolate a c load from the TS1001?s output figure 6 : TS1001 transient response for r iso = 50k ? and c load = 500pf . v in v out
TS1001 page 10 TS1001ds r1p0 rtfds configuring the TS1001 as nanowatt analog comparator although optimized for use as an operational amplifier, the TS1001 can also be used as a rail-to- rail i/o comparator as illu strated in figure 7. external hysteresis can be employed to minimize the risk of output oscillati on. the posit ive feedback circuit causes the input threshold to change when the output voltage changes state. the diagram in figure 8 illustrates the ts 1001?s analog comparator hysteresis band and output transfer characteristic. the design of an analog comparator using the TS1001 is straightforward. in this application, a 1.5- v power supply (v dd ) was used and the resistor divider network formed by rd1 and rd2 generated a convenient reference voltage (v ref ) for the circuit at ? the supply voltage, or 0.75v, while keeping the current drawn by this resistor divider low. capacitor c1 is used to filter any extraneous noise that could couple into the TS1001?s inverting input. in this application, the desired hysteresis band was set to 100mv (v hyb ) with a desired high trip-point (v hi ) set at 1v and a desired low trip-point (v lo ) set at 0.9v. since the TS1001 is a very low supply current amplifier (0.6a, typical), it is desired that the design of an analog comparator using the TS1001 should also use as little current as practical. the first step in the design, therefore, was to set the feedback resistor r3: r3 = 10m ? calculating a value for r1 is given by the following expression: r1 = r3 x (v hyb /v dd ) substituting v hyb = 100mv, v dd = 1.5v, and r3 = 10m ? into the equation above yields: r1 = 667k ? the following expression was then used to calculate a value for r2: r2 = 1/[v hi /(v ref x r1) ? (1/r1) ? (1/r3)] substituting v hi = 1v, v ref = 0.75v, r1 = 667k ? , and r3 = 10m ? into the above expression yields: r2 = 2.5m ? printed circuit board layout considerations even though the TS1001 operates from a single 0.65v to 2.5v power supply and consumes very little supply current, it is always good engineering practice to bypass the power supplies with a 0.1 f ceramic capacitor placed in close proximity to the v dd and v ss (or gnd) pins. good pcb layout techniques and analog ground plane management improve the performance of any analog circuit by decreasing the amount of stray capacitance that could be introduced at the op amp's inputs and outputs. excess stray capacitance can easily couple noise into the input leads of the op amp and excess stray capacitance at the output will add to any external capaciti ve load. therefore, pc board trace lengths and external component leads should be kept a short as practical to any of the TS1001?s package pins. second, it is also good engineering practice to route/remove any analog ground plane from the inputs and the output pins of the TS1001. figure 8: analog comparator hysteresis band and output switching points. figure 7: a nanowatt analog comparator with user- programmable hysteresis.
TS1001 touchstone semiconductor, inc. page 11 630 alder drive, milpitas, ca 95035 TS1001ds r1p0 +1 (408) 215 - 1220 ? www.touchstonesemi.com rtfds package outline drawing 5-pin sc70 package outline drawing (n.b., drawings are not to scale) information furnished by touchstone semic onductor is believed to be accurate and reli able. however, touchstone semiconductor do es not assume any responsibility for its use nor for any infringements of patents or other rights of third parties that may result fro m its use, and all information provided by touchstone semic onductor and its suppliers is provided on an as is basis, without warranty of any kind. touchstone semiconductor reserves the right to change product specifications and pr oduct descriptions at any time without any a dvance notice. no license is granted by implication or otherwise unde r any patent or patent rights of touchstone semiconductor. touchs tone semiconductor assumes no liability for applic ations assistance or customer product des ign. customers are responsible for their products and applications using touchstone semiconductor components. to minimize the risk a ssociated with customer products and applications , customers should provide adequate design and operating safeguards . trademarks and registered trademarks are the property of the i r res p ective owners.

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